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AD8348
MXIN 19
1000pF
MXIN
LO
4 5
3 1
1:1
MXIP 18
MXIP
1000pF
60.4 ?
1000pF
1000pF
AD8348
Figure 53. Driving the MX Inputs from a Differential Source
1
LOIP
LOIN 28
+V S
If the MX inputs are to be driven from a single-ended 50 Ω source,
a 4:1 balun can be used to transform the 200 Ω impedance of
the inputs to 50 Ω while performing the required single-ended-
0.1μF
TO BASEBAND
I ADC
100pF
2
3
4
VPOS1 COM1 27
IOPN QOPN 26
IOPP QOPP 25
TO BASEBAND
Q ADC
to-differential conversion. The recommended transformer is the
M/A-COM ETK4-2T.
V REF
5
6
VCMO
IAIN
ENVG 24
QAIN 23
+V S
7
COM3
COM3 22
MXIN 19
1000pF
1.02k ?
8
IMXO
QMXO 21
1.24k ?
V CMO
1μF
ETK4-2T
9
COM2 VPOS3 20
100pF
0.1μF
+V S
MXIP 18
1000pF
MXIP
1000pF
10
IFIN
MXIN 19
1000pF
Figure 54. Driving the MX Inputs from a Single-Ended 50 Ω Source
BASEBAND OUTPUTS
IF INPUT
Z O = 200 ?
+V S
0.1μF
1000pF
100pF
100pF
11
12
13
IFIP
VPOS2
IOFS
MXIP 18
VGIN 17
QOFS 16
1000pF
100pF
The baseband amplifier outputs, IOPP, IOPN, QOPP, and QOPN,
V REF
1000pF
14
VREF
ENBL 15
100pF
+V S
should be presented with loads of at least 2 kΩ (single-ended to
ground). They are not designed to drive 50 Ω loads directly. The
AD8362
typical swing for these outputs is 2 V p-p differential (1 V p-p
1
COMM ACOM 16
single-ended), but larger swings are possible as long as care is taken
to ensure that the signals remain within the lower limit of 0.5 V
1μF
1μF
2
3
CHPF
DECL
VREF 15
VTGT 14
and the upper limit of V S ? 1 V of the output swing. To achieve
a larger swing, it is necessary to adjust the common-mode bias of
1μF
1μF
4
INHI
VPOS 13
100pF
0.1μF
+V S
the baseband output signals. Increasing the swing can have the
5
INLO
VOUT 12
benefit of improving the signal-to-noise ratio of the baseband
6
DECL
VSET 11
V SET
amplifier output.
7
PWDN ACOM 10
1μF
When connecting the baseband outputs to other devices, care
8
COMM
CLPF 9
should be taken to ensure that the outputs are not capacitively
loaded by approximately 20 pF or more. Such loads could
potentially overload the output or induce oscillations. The effect
of capacitive loading on the baseband amplifier outputs can be
mitigated by inserting series resistors of approximately 200 Ω.
OUTPUT DC BIAS LEVEL
The dc bias of the mixer outputs and the baseband amplifier
inputs and outputs is determined by the voltage that is driven
onto the VCMO pin. The range of this voltage is typically
between 500 mV and 4 V when operating with a 5 V supply.
To achieve maximum voltage swing from the baseband amplifiers,
VCMO should be driven at 2.25 V; this allows a swing of up to
7 V p-p differential (3.5 V p-p single-ended).
INTERFACING TO DETECTOR FOR AGC OPERATION
The AD8348 can be interfaced with a detector such as the
AD8362 rms-to-dc converter to provide an automatic signal-
leveling function for the baseband outputs.
Figure 55. AD8362 Configuration for AGC Operation
Assuming the I and Q channels have the same rms power, the
mixer output (or the output of the baseband filter) of one channel
can be used as the input of the AD8362. The AD8362 should be
operated in a region where its linearity error is small. Also, a
voltage divider should be implemented with an external resistor
in series with the 200 Ω input impedance of the AD8362 input.
This attenuates the AD8348 mixer output so that the AD8362
input is not overdriven. The size of the resistor between the
mixer output and the AD8362 input should be chosen so that
the peak signal level at the input of the AD8362 is about 10 dB
less than the approximately 10 dBm maximum of the AD8362
dynamic range.
The other side of the AD8348 baseband output should be
loaded with a resistance equal to the series resistance of the
attenuating resistor in series with the AD8362’s 200 Ω input
impedance. This resistor should be tied to the source driving
VCMO so that there is no dc drawn from the mixer output.
Rev. A | Page 21 of 28
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